Adaptive cancellation of fixed interferers

ABSTRACT

An improved base station which cancels the effects of known fixed interference sources produces a signal substantially free from the interference sources thereby increasing total channel capacity. The adaptive interference canceler system includes a main antenna for receiving signals from other communication stations and at least one directional antenna directed toward an interference source. The main and directional antennas are coupled together such that an output signal substantially free from the interference is generated.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation of application Ser. No. 09/038,922,filed on Mar. 12, 1998.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to wireless digital communication systems.More particularly, the present invention relates to an adaptiveinterference canceler included within telecommunication base stationsand uses at least one auxiliary antenna in conjunction with a primaryantenna for increasing the capacity of the telecommunication system bysubstantially reducing interference produced by one or more knowninterference sources proximate to the base station.

2. Description of the Prior Art

Over the last decade consumers have become accustomed to the convenienceof wireless communication systems. This has resulted in a tremendousincrease in the demand for wireless telephones, wireless datatransmission and wireless access to the Internet. The amount ofavailable RF spectrum for any particular system is often quite limiteddue to government regulation and spectrum allotments.

CDMA communication systems have shown promise in the effort to provideefficient utilization of the RF spectrum. At least one brand of CDMAsystems, Broadband Code Division Multiple Access™ or B-CDMA™communication systems available from InterDigital CommunicationsCorporation, permit many communications to be transmitted over the samebandwidth, thereby increasing the capacity of the allotted RF spectrum.In B-CDMA™ communication systems, a data signal at the transmitter ismixed with a pseudorandom “spreading code” to spread the informationsignal across the entire transmission bandwidth or spectrum employed bythe communication system. Afterwards, the spread spectrum signal ismodulated with an RF carrier signal for transmission. A receiverreceives the transmitted RF carrier signal and down converts the signalto a spread baseband signal. The spread data signal is despread bymixing the locally generated pseudorandom spreading code with the spreadsignal.

In order to detect the information embedded in a received signal, areceiver must use the same pseudorandom spreading code that was used tospread the signal. Signals which are not encoded with the pseudorandomcode of the receiver appear as background noise to the receiver.However, signal frequencies within the transmission bandwidth contributeto the overall background noise making it difficult for receivers toproperly detect and receive signals. A subscriber may increase the powerof his transmitted signal to compensate, but overpowering interfereswith the reception of other communication channels sharing the samecommunication bandwidth.

The allocated transmission bandwidths of many CDMA communication systemsapproach or share frequencies with other communication systems, such asmicrowave relaying or cellular communication systems. These systems maypresent interference signals which can greatly exceed the power of theCDMA communication signals in specific regions of the transmissionbandwidth.

Applicants have recognized the need to decrease the amount ofinterference from identified manmade interferers in order to efficientlyincrease the allocated spectrum capacity of a CDMA communication system.

SUMMARY OF THE INVENTION

The present invention provides an improved base station which cancelsthe effects of known fixed interference sources to produce a signalsubstantially free from the interference sources.

In one embodiment, an antenna system in conjunction with a base stationis deployed at a location with one or more known interference sources.The antenna system includes a main antenna for receiving signals fromother communication stations and at least one directional antennadirected toward an interference source. The main and directionalantennas are coupled to an adaptive canceler, which weights signalsreceived by the directional antennas and sums the weighted signals toproduce a cancellation signal. The adaptive canceler subtracts thecancellation signal from the signals received by the main antenna toprovide an output signal substantially free from the interferencegenerated by the one or more known interference sources. The adaptivecanceler may use a plurality of feedback loops to implement a least meansquare (LMS) algorithm to properly weight the directional antennasignals.

Accordingly, it is an object of the present invention to decrease theamount of interference produced from manmade interference sources thatis processed as a received CDMA communication signal.

Other advantages may become apparent to those skilled in the art afterreading the detailed description of the preferred embodiment.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a communication network embodiment of the present invention.

FIG. 2 shows propagation of signals between a base station and aplurality of subscriber units.

FIG. 3A is a diagram of a base station of the present invention.

FIG. 3B is a diagram of the base station of the present invention withfour coplanar feeds (n=4).

FIG. 4 is a diagram of a first embodiment of an RF adaptive canceler ofthe present invention.

FIG. 5 is a detailed diagram of a base station of the present invention.

FIG. 6 is a diagram of a vector correlator.

FIG. 7 is a diagram of a phase-locked loop (PLL).

FIG. 8A is a diagram of a second embodiment of a base station of thepresent invention.

FIG. 8B is a diagram of the second embodiment of the base station withfour coplanar feeds (n=4) for both first and second auxiliary antennas.

FIG. 9 is a diagram of a second embodiment of an RF adaptive canceler ofthe present invention.

FIG. 10 is a diagram of a third embodiment of a base station of thepresent invention.

FIG. 11 is a diagram of a fourth embodiment of a base station of thepresent invention.

FIG. 12 is a diagram of a fifth embodiment of a base station of thepresent invention.

FIG. 13 is a diagram of a sixth embodiment of a base station of thepresent invention.

DESCRIPTION OF THE PREFERRED EMBODIMENTS

Presently preferred embodiments are described below with reference tothe drawing figures wherein like numerals represent like elementsthroughout.

A communication network 21 embodying the present invention is shown inFIG. 1. The communication network 21 generally comprises one or morebase stations 23, each of which is in wireless communication with aplurality of subscriber units 25, which may be fixed or mobile. Eachsubscriber unit 25 communicates with either the closest base station 23or the base station 23 which provides the strongest communicationsignal. The base stations 23 also communicate with a base stationcontroller 27, which coordinates communications among base stations 23.The communication network 21 may also be connected to a public switchedtelephone network (PSTN) 29, wherein the base station controller 27 alsocoordinates communications between the base stations 23 and the PSTN 29.Preferably, each base station 23 communicates with the base stationcontroller 27 over a wireless link, although a land line may also beprovided. A land line is particularly applicable when a base station 23is in close proximity to the base station controller 27.

The base station controller 27 performs several functions. Primarily,the base station controller 27 provides all of the operations,administrative and maintenance (OA&M) signaling associated withestablishing and maintaining all of the wireless communications betweenthe subscriber units 25, the base stations 23, and the base stationcontroller 27. The base station controller 27 also provides an interfacebetween the wireless communication system 21 and the PSTN 29. Thisinterface includes multiplexing and demultiplexing of the communicationsignals that enter and leave the system 21 via the base stationcontroller 27.

Referring to FIG. 2, the propagation of signals between a base station23 and a plurality of subscriber units 25 is shown. A two-waycommunication path 31 comprises a forward signal 33 transmitted (TX)from the base station 23 to a subscriber 25 and a return signal received35 (RX) by the base station 23 from the subscriber 25. The signalbetween the base station 23 and the subscriber 25 includes thetransmission of a global pilot signal. The pilot signal is a RFmodulated spreading code with no data modulation. The pilot signal isused for synchronizing the base station 23 with the subscriber 25. Acommunication channel is established upon synchronization.

Referring to FIG. 3A, a base station 23 of the present inventionincludes a main antenna 37 and an auxiliary antenna 39 which are coupledto a RF adaptive canceler 41. The output of the adaptive canceler 41 iscoupled to a RF receiver 43, which is coupled to a plurality of modems45 ₁-45 _(n). Each CDMA communication channel is spread with a uniquespreading code. The plurality of modems 45 ₁-45 _(n) enable simultaneousprocessing of multiple CDMA communications, each processing acommunication associated with a different spreading code.

Signals which are not encoded with the proper pseudorandom code appearas background noise or interference to a particular communication. Inaddition, the level of noise may increase due to a known interferer 47.For example, a local radio station may be an interferer because itbroadcasts a signal in the same transmission bandwidth used by the basestation 23. To overcome the interference, the subscriber units 25 mustincrease their transmission power exacerbating the level of backgroundnoise since the increase in power by the subscribers 25 increases thelevel of noise thereby decreasing the number of subscribers 25 which canbe accommodated by the base station 23.

In order to cancel the effects of the known interferer 47, the auxiliaryantenna 39 is directed toward the source of interference 47. Theauxiliary antenna 39 architecture is highly focused and directional suchthat the only large signal received by the auxiliary antenna 39 is thesignal from the interferer 47 and not the signals from the subscriberunits 25. The auxiliary antenna 39 has a plurality of coplanar feeds 49₁-49 _(n) for receiving a plurality of replicas of the signaltransmitted by the interferer 47. One skilled in the art should clearlyrecognize that the number of individual feeds used is based upon thespecification of a given application. A preferred embodiment having fourcoplanar feeds (n=4) is shown in FIG. 3B. Referring back to FIG. 3A,each interference replica has a different phase corresponding to thecoplanar feed 49 ₁-49 _(n) position in free space. After theinterference replicas are received through the coplanar feeds 49 ₁-49_(n), the interference replicas are coupled to the RF adaptive canceler41. The coplanar feeds 49 ₁-49 _(n) located in the auxiliary antenna 39are preferably spaced one-quarter to one-half wavelength of the carrierfrequency apart.

Referring to FIG. 4, the RF adaptive canceler 41 removes theinterference signals from the signal received by the main antenna 37 sothat the overall background noise is greatly reduced. This isaccomplished by providing the RF adaptive canceler 41 with circuitry forimplementing a least mean square (LMS) algorithm or other adaptivealgorithm to provide proper weights to each of the interference signalsreceived by the coplanar feeds 49 ₁-49 _(n). The proper weights for eachinterference replica are obtained when the adaptive canceler 41 reachessteady state. These weighted interference replicas are summed to providea combined interference signal, which is subtracted from the signal fromthe main antenna 37 thereby deriving a signal substantially free fromthe interference source 47.

The RF adaptive canceler 41 includes weighting mixers 51 ₁-51 _(n),integrating mixers 53 ₁-53 _(n), operational amplifiers 55 ₁-55 _(n),integrators 57 ₁-57 _(n), a summation unit 58, and summer 61. Weightingmixers 51 ₁-51 _(n) and integrating mixers 53 ₁-53 _(n) receive theinterference replicas from feeds 49 ₁-49 _(n) respectively. Eachcorresponding weighting mixer 51 ₁-51 _(n), operational amplifiers 55₁-55 _(n) and integrators 57 ₁-57 _(n), are operatively coupled toproduce respective weights W₁-W_(n) which are mixed with the respectiveinterference replica via mixers 51 ₁-51 _(n). The weights W₁-W_(n) areinitially zero so that the interference replicas initially received passto the summation unit 58 without adjustment. The output of the summationunit 58 is a combined interference signal and is subtracted from thetotal signal received from the main antenna 37 using the summer 61.

The adaptive canceler 41 outputs the received signal absent the knowninterference 47 to both the RF receiver 43 and the mixers 53 ₁-53 _(n)to create multiple feedback loops for implementing feed 49 ₁-49 _(n)weight W₁-W_(n) adjustments. The signals output from the integratingmixers 53 ₁-53 _(n) are fed to amplifiers 55 ₁-55 _(n) and integrators57 ₁-57 _(n) to adjust the weights W₁-W_(n) which are input to weightingmixers 51 ₁-51 _(n). The amplified and integrated signals are mixed withthe interference replicas. This completes the LMS circuit. Once thesignal input levels to the integrators 57 ₁-57 _(n) are zero, theadaptive canceler 41 is in steady state and the weights W₁-W_(n) remainconstant until a perturbation in the interference is experienced.

The outputs of the integrators 57 ₁-57 _(n) continuously provideappropriate weights W₁-W_(n) via the feedback loops to the summationunit 59. The combined interference signal output from summation unit 59is subtracted from the signal received from main antenna 37 by thesummer 61, so that the signals received from the main antenna 37 areoutput 63 from the RF adaptive canceler 41 substantially free from theinterference produced by the fixed interferer 47.

Referring back to FIG. 3A, the adaptive canceler 41 is coupled to the RFreceiver 43 which demodulates the RF signal removing the carrierfrequency and outputting a baseband signal to the modems 45 ₁-45 _(n).The modems 45 ₁-45 _(n) search through possible phases of the resultingbaseband signal until they detect the correct phase. Phase-distortedcopies of the communication signal or “multiples,” are compensated forby overlaying them on the correct phase which results in increased gain.This function is performed by an adaptive matched filter (AMF) 65 whichoperates in conjunction with phase correcting coefficients determined bya vector correlator or rake receiver 67 with a carrier recoveryphase-locked loop (PLL) 69 (FIG. 5).

More specifically, each of the modems 45 ₁-45 _(n) includes ananalog-to-digital (A/D) converter 71 which quantizes the baseband signalinto a digital signal with the assistance of a tracker 73. The tracker73 directs the A/D converter 71 to sample the strongest analogrepresentation of the data being transmitted to the base station 23 toprovide an accurate digital signal. The digital signal may include aplurality of data signals and a pilot signal.

As is well known in this art, CDMA communication units use a pilotsignal to provide synchronization of a locally generated pseudorandomcode with the pseudorandom code transmitted by the transmitting station,and to provide a transmission power reference during initial powerramp-up. Typically, a base station 23 transmits the pilot signal to theremote units 25 to provide synchronization of locally generatedpseudorandom codes with the transmitted pseudorandom code. The pilotsignal is a pseudorandom sequence of complex numbers having a magnitude(real component) of one and phase (imaginary component) of zero.

The digital pilot signal will suffer from the same distortion as thedigital data signal, since they are both transmitted within the RFsignal. Accordingly, the vector correlator 67, receives the pilot signaland determines in conjunction with a phase-locked loop (PLL) 69 filtercoefficients based on the distortion of the pilot signal. The derivedcoefficients represent the distortion or errors of the data signal. Thedata signal/CDMA communication signal, which is directed to the AMF 65,is processed by the AMF 65 according to the filter coefficientsgenerated by the vector correlator 67 in combination with the PLL 69.

As disclosed in U.S. patent application Ser. No. 08/266,769 and U.S.patent application Ser. No. 08/871,109, which are incorporated byreference as if fully set forth herein, vector correlators inconjunction with phase-locked loop circuitry have been utilized toproduce filter coefficients to correct for multipath distortion. In thepresent invention, the vector correlator 67 and PLL 69 generate filtercoefficients associated with multipath distortion.

Referring to FIG. 6, the vector correlator 67 provides an estimate ofthe complex channel impulse response, having real and imaginarycomponents, of the bandwidth over which the CDMA communication signal istransmitted. The vector correlator 67 has a plurality of independentelements or “fingers” 75 ₁-75 _(n) preferably eleven, wherein thepseudorandom pilot signal input to each finger 75 ₁-75 _(n) is delayedτ₁-τ_(n) by one chip to define a processing “window.” A typicalprocessing window would include eleven chips. The pilot signal is inputto each element 75 ₁-75 _(n).

Each element 75 ₁-75 _(n) performs an open-loop estimation of thesampled impulse response of the RF channel. Thus, the vector correlator67 produces noisy estimates of the sampled impulse response at evenlyspaced intervals. Accordingly, the signal analysis performed by thevector correlator 67 determines phase distortions occurring at differentpoints within the processing window, for example, distortionattributable to multipath interference.

In operation, each element 75 ₁-75 _(n) of the vector correlator 67receives a locally generated pseudorandom pilot signal. The signalsupplied to the vector correlator 67 from the A/D converter 71 is inputto each element. Mixers 77 ₁-77 _(n) mix the locally generated pilotpseudorandom code with the received signal to despread the pilot signal.The delay units τ₁-τ_(n) impart a one chip delay on the despread pilotsignal. Each element 75 ₁-75 _(n) receives a carrier offset phasecorrection signal from the PLL 69, which is mixed with the despreadpilot signal in each element 75 ₁l-75 _(n) by mixers 79 ₁-79 _(n) toprovide sample impulse response estimates. The vector correlator 67further includes a plurality of low-pass filters 81 ₁-81 _(n) which arecoupled to each mixer 79 ₁-79 _(n) to smooth each corresponding sampleimpulse response estimate. The complex conjugates of each smoothedsampled impulse response estimate are used as the filter coefficients,or weights, for the AMF 65. In addition, the complex conjugate of eachsmoothed sampled response is mixed with the despread pilot signal bymixers 83 ₁-83 _(n). The summation unit 85 receives the outputs ofmixers 83 ₁-83 _(n) and outputs the combined despread pilot signal whichis substantially free from multipath distortion.

The carrier recovery PLL 69 processes the output of the vectorcorrelator 67 to estimate and correct the phase error or difference dueto RF carrier signal offset. The offset may be due to internal componentmismatches and/or RF distortion. Component mismatches between thesubscriber oscillator and the receiver oscillator may cause slightlydifferent oscillator outputs. These component mismatches can be furtherexacerbated by local and environmental conditions, such as the heatingand cooling of electronic components which may affect the temperaturecoefficient of the various components. With respect to RF channeldistortion. Doppler effects caused by the motion of the receivingstations relative to the transmitter station or a mismatched reflectormay cause the RF carrier to become distorted during transmission. Thismay result in a RF carrier offset. The PLL 69 architecture is preferablyexecuted in a programmable digital signal processor (DSP).

Referring to FIG. 7, the continuously adjusted-bandwidth PLL 69comprises a mixer 87, a normalizing unit 89, an arctangent analyzer 91,a phase-locked loop filter 93, a voltage controlled oscillator (VCO) 95and a bandwidth control section 97. The mixer 87 receives the outputfrom the vector correlator 67 which is the despread pilot signalprocessed to correct for channel distortion due to multipath effects.The despread pilot signal is mixed with a correction signal from the VCO95 to produce a complex error signal which is coupled to the normalizingunit 89. The normalized signal is coupled to the arctangent analyzer 91.The arctangent analyzer 91 outputs a phase angle derived from thecomplex (number) error signal. The bandwidth control section 97continuously monitors the quantized phase error signal and generates acontrol signal to control the bandwidth of the phase locked-loop filter93. The signal output for the phase-locked loop filter 93 is transmittedto the VCO 95. The VCO 95 outputs a feedback signal to mixer 87. Theoutput from phase-locked loop filter 93 indicates carrier-offset phaseerror. The process is repeated until a complex error signal output fromthe mixer 87 is at a minimum. Optimum performance of the modem 45 ₁ willnot occur until the vector correlator 67 and PLL 69 have reached amutually satisfactory equilibrium point.

The vector correlator 67 outputs weighting coefficients to the AMF 65.The AMF 65 processes the communication signal to compensate for channeldistortion due to multipath effects. This compensation increases thegain of the signal by, in effect, overlaying delayed replicas of thesignal. The AMF 65 outputs the filtered signal to a plurality of channeldespreaders 99. The despread channel signals are coupled to Viterbidecoders 101 for decoding the forward error correction (FEC) encodeddata signals.

The channel despreaders 99 couple to the Viterbi decoders 101 whichfunction as described in copending application Ser. No. 08/871,008,which is incorporated by reference as if fully set forth of theconvolutional encoder (not shown) of a subscriber unit 25. The Viterbidecoders 101 decodes the FEC signal rendering the original data signal.The resulting data signal can be output either digitally or converted toanalog with a digital to analog converter (DAC) 103. The Viterbidecoders 101 also perform a bit error rate (BER) 106 calculation whichis coupled to an automatic power control (APC) unit 105.

The APC unit 105 determines whether the transmission signal strength ofthe received data signal should be increased or decreased to maintain anacceptable bit error rate based upon the estimate of the interferenceprovided by the channel despreaders 99. The BER 106 output from theViterbi decoder 101 is coupled to the APC unit 105 to adjusttransmission power. The APC unit 105 calculates a signal-to-interferenceratio (SIR_(t)) threshold for the system to maintain. An adjustableinput representing a desired quality of service is input into the APCunit 105 as a combination of desired bit error (BER₀) 107 and signal tointerference ratio (SIR₀) 108. The choice of quality depends whether thesystem is providing simple voice communication or a more sophisticatedtransmission such as facsimile. The quality determination is performedduring decoding. The relationshipSIR _(t) =SIR ₀ +k(BER−BER ₀)  Eqn. 1determines SIR_(t) 109 which is the sought interference threshold. Aweight or gain k adjusts the deviation from the desired BER₀ and derivesthe SIR_(t) from the base SIR₀ which is used to adjust transmissionpower. This instruction is conveyed within the reverse signal to asubscriber.

A base station 111 in accordance with a second embodiment of the presentinvention will be explained with reference to FIG. 8A. The base station111 includes a main antenna 113 and first 115 and second 117 auxiliaryantennas which are coupled to an RF adaptive canceler 119. The first 115and second 117 auxiliary antennas are directed at separate knowninterferers 121, 123. The adaptive canceler 119 is coupled to an RFreceiver 125, which is connected to a plurality of modems 127 as in thefirst embodiment. The RF adaptive canceler 119 cancels the effects ofthe two interferers. If additional known interferers are present in theoperating region of main antenna 113, additional auxiliary antennasfacing the additional interferers can be added to cancel the effects ofthe additional interferers.

The first auxiliary antenna 115 has a plurality of coplanar feeds 129₁-129 _(n) for receiving replicas of the interference signal from theinterferer 121. An embodiment having four coplanar feeds (n=4) for bothfirst and second auxiliary antennas is shown in FIG. 8B. Referring backto FIG. 8A, the coplanar feeds 129 ₁-129 _(n) are preferably one quarterto one half wavelength apart. The second auxiliary antenna 117 also hasa plurality of coplanar feeds 131 ₁-131 _(n) for receiving the replicasof the interference signal from the second interferer 123. The coplanarfeeds 131 ₁-131 _(n) are preferably a one quarter to one half wavelengthapart. In addition, both first 115 and second 117 auxiliary antennas arefocused such that substantially only the signals from the first 121 andsecond 123 interferers will be received by the auxiliary antennasrespectively, and the signals from a subscriber unit 25 will not bereceived by the auxiliary antennas. After all the interference replicasare received through the coplanar feeds 129 ₁-129 _(n) and 131 ₁-131_(n), the replicas of the first 115 and second 117 auxiliary antennasare passed to the RF adaptive canceler 119. Each replica has a differentphase corresponding to the position of each coplanar feed.

Referring to FIG. 9, an examination reveals that this embodiment 111 isthe same as the adaptive canceler 41 shown in FIG. 4 with the inputsfrom auxiliary antenna 30 now comprising interference samples from thefirst auxiliary antenna 115 feeds 129 ₁-129 _(n) and second auxiliaryantenna 117 feeds 131 ₁-131 _(n). The adaptive canceler of the presentinvention can input a plurality of directional interference sourcescomprised of a plurality of multiphase samples and perform a uniform LMSalgorithm to remove the interference samples.

Referring to FIG. 10, a third alternative embodiment of a base station141 made in accordance with the present invention is shown. The basestation 141 includes a main antenna 143 and a narrow beam directionalantenna 145 (auxiliary antenna) coupled to an interference canceler 147.The interference canceler 147 includes a summer 149 and an amplifier151. The interference cancellation method involves directing the narrowbeam directional antenna 145 towards a fixed interferer (not shown) asin the previous embodiments, weighting the signal received by the narrowbeam directional antenna 145 by a factor α and subtracting it from thesignal received from the main antenna 143 using a summer 149. Theresulting signal is used for demodulating the transmitted data. Thechoice of the weighting factor α determines how much reduction in thefixed interference is obtained.

The total power received by the main antenna 110 in the absence of anyinterference cancellation scheme is:P ₀ =KP+P _(i)  Eqn. 2where K equals the total number of users, P equals the power received atthe base station from a user who is not in the narrow beam of thesecondary antenna, and P_(i) is the power received from a fixedinterferer.

With both the main 143 and narrow beam 145 antennas, the total powerreceived by the main antenna 110 isP _(p)=(K−M)P+MP*+P _(i)  Eqn. 3where M equals the number of users within the narrow beam of the narrowbeam antenna 145, and P* is the power received from a user who is in thenarrow beam of a narrow beam antenna 145. The total power received bythe narrow beam antenna 145 isP _(s) =MP*+P _(i).  Eqn. 4The signal that is to be used in demodulation has the total power, whichisP _(t) =P _(p) −αP _(s)=(K−M)P+MP*+P _(i) −αMP*−αP _(i),  Eqn. 5or equivalentlyP _(t)=(K−M)P+M(1−α)P*+(1−α)P _(i).  Eqn. 6As a result of the automatic power control, all users' have the samesignal strength contributing to the total power P_(t). This impliesP=(1−α)P*,  Eqn. 7$\begin{matrix}{P^{*} = {\frac{P}{1 - \alpha}.}} & \text{Eqn.~~8}\end{matrix}$Therefore, P_(t) can now be written asP _(t) =KP+(1−α)P _(i).  Eqn. 9By comparing equation 9 to equation 3, the contribution of the fixedinterferer when comparing signals received by the main antenna only tothat received by the combined main-antenna auxiliary-antenna system hasdecreased by a factor of (1−α). For example, if α=0.9, the interferencehas been reduced by 10 dB. Thus, there is an effective spatialattenuation in the direction of the narrow beam antenna. Thisattenuation will affect not only the interferer, but users that are inthe narrow beam path as well. To compensate, users within the path ofthe narrow beam directional antenna 145 must have antenna gains that arehigher by a factor of 1/(1−α). This can be achieved by giving theseparticular users higher gain antennas. This is practical because therewill be only a few users within the narrow beam of the narrow beamdirectional antenna 145.

The weighted interference signal from amplifier 151 is subtracted fromthe signals received by way of main antenna 143 by summer 149 so thatthe signals from main antenna 143 are passed from the interferencecanceler 147 substantially free from the known interferers to a RFreceiver 153 which demodulates and removes the carrier frequency. Thebaseband signal output by the RF receiver 153 is processed by the modems155 ₁-155 _(n) as discussed in the first embodiments.

Referring to FIG. 11, a fourth alternative embodiment of a base station159 is shown. The base station 159 includes a main antenna 161 and aplurality of narrow beam directional antennas 163 ₁-163 _(n) (auxiliaryantennas) coupled to an interference canceler 165. The interferencecanceler 165 includes a summation unit 167 and a plurality of weightingamplifiers 169 ₁-169 _(n) coupled to each narrow beam directionalantenna 163 ₁-163 _(n). The interference cancellation method involvesdirecting each narrow beam directional antenna 163 ₁-163 _(n) toward acorresponding fixed interferer as in the second alternative embodiment,weighting the signals received by the narrow beam directional antennas163 ₁-163 _(n) by corresponding weighting factors α₁-α_(n) andsubtracting the weighted signals from the signal received by way of themain antenna 161 using summation unit 167. The resulting signal is thenused for demodulation of user data. The choice of the weighting factorsα₁-α_(n) determines the reduction in the fixed interference as explainedin the third embodiment.

The weighted interference signals from the amplifiers 169 ₁-169 _(n) aresubtracted from the signals received by the main antenna 161 bysummation unit 167 so that the signals from main antenna 161 are passedfrom the interference canceler 165 substantially free from the knowninterferers to a RF receiver 171 which demodulates and removes thecarrier frequency. The baseband signal output by the RF receiver 171 isprocessed by the modems 173 ₁-173 _(n) as discussed in the firstembodiment.

Referring to FIGS. 12 and 13, fifth 179 and sixth 199 alternativeembodiments are shown similar to the architectures in FIGS. 10 and 11differing in that the RF receivers are coupled directly to the antennas,demodulating the RF signals to baseband first and then performing thesubtraction of the interferers received from the narrow beam directionalantennas. As one skilled in this art would recognize, the processing ofthe received signal and individually received interferers is at afrequency bandwidth much less than the transmission frequency bandwidth.Both the interference cancelers employed in the fifth 179 and sixth 199alternative embodiments functions identically to those described in thethird and fourth embodiments shown in FIGS. 10 and 11.

The alternative embodiments shown in FIGS. 10-13 require synchronizationof the received signals before subtraction can be made. This means thatthe cable lengths and other passive delays in the receive path of themain antenna and the auxiliary antenna(s) must be matched. The mainantenna and auxiliary antenna(s) must be placed relatively close to eachother to make sure that the receive signal from the antennas are notsubject to different channel responses.

Although the invention has been described in part by making detailedreference to certain specific embodiments, such detail is intended to beinstructive rather than restrictive. It will be appreciated by thoseskilled in the art that many variations may be made in the structure andmode of operation without departing from the spirit and scope of theinvention as disclosed in the teachings herein.

1. An interference cancellation system for use in conjunction with abase station having a main antenna for receiving signals from aplurality of remote users, wherein at least one interference source isknown, the system comprising: at least one directional antenna directedtoward said at least one interference source, said antenna having aplurality of coplanar feeds that are located one quarter to one halfwavelength apart from each other, each coplanar feed for receiving an RFsignal; means for weighting said RF signals received by said pluralityof coplanar feeds to produce a cancellation signal; first summing meansfor summing said weighted signals using a least mean square (LMS)algorithm; and second summing means for summing said cancellation signalwith signals received from said main antenna to produce an output signalsubstantially free from interference.
 2. The system of claim 1 whereinsaid weighting is performed using a predetermined factor α.
 3. Thesystem of claim 2 wherein each said user is located within the narrowbeam path of the directional antenna, and each antenna gain of remoteuser communicating with said base station is greater than 1(1−α)relative to the main antenna.
 4. The system of claim 1, wherein saidoutput signal is demodulated by an RF receiver to produce a basebandsignal, said receiver being coupled to a plurality of modems for phasecorrection of said baseband signal.
 5. The system of claim 4, wherebyeach of said modems comprises: means for producing a digital signal byquantizing the baseband signal, said digital signal comprising a datasignal and a pilot signal; means for deriving filter coefficients basedon phase error due to RF carrier offset of the data signal; means forcompensating for channel distortion due to multipath effects; means fordetermining bit error rate; and means for automatic power controlresponsive to the bit error rate.
 6. The system of claim 4, wherein eachsaid modem comprises: an A/D converter coupled to a tracker; a vectorcorrelator coupled to the output of the A/D converter; a carrierrecovery phase-locked loop unit coupled to the vector correlator forproducing filter coefficients in conjunction with the vector correlator;an adaptive matched filter (AMF) with an input coupled to the A/Dconverter and the vector correlator and an output coupled to thetracker; a plurality of channel despreaders coupled to the AMF output; aViterbi decoder coupled to the output of said plurality of channeldespreaders; and an automatic power control (APC) unit coupled to theViterbi decoder.
 7. A method for interference cancellation for use inconjunction with a base station having a main antenna for receivingsignals from a plurality of remote users, wherein at least oneinterference source is known, comprising the steps of: directing atleast one directional antenna toward said at least one interferencesource, each directional antenna having a plurality coplanar feeds thatare located one quarter to one half wavelength apart from each other,each coplanar feed for receiving an RF signal; and cancelling aninterference signal generated by said at least one known interferencesource, wherein said cancelling step further comprises: weighting the RFsignals received by said coplanar feeds; summing the weighted signalsusing a least mean square (LMS) algorithm to produce a cancellationsignal; summing the cancellation signal with signals received from themain antenna to produce an output signal substantially free frominterference; and comparing feedback from the output signal to theweighted signal until steady state is achieved.